Negative feedback is often referred to as shunt feedback and here in this application we will use it in conjunction with emitter degeneration. How is this accomplished? Negative feedback or shunt feedback is accomplished by adding one resistor and a capacitor between collector and base of our transistor. For this exercise I'm going to go to an r.f. application and replace a resistor with a choke, it could easily have been a transformer


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What is negative feedback?

Negative feedback is often referred to as shunt feedback and here in this application we will use it in conjunction with emitter degeneration.

Shunt Feedback and Emitter Degeneration

How is this accomplished? Quite easy! Shunt feedback is accomplished by adding one resistor and a capacitor between collector and base of our transistor. For this exercise I'm going to go to an r.f. application and replace resistor R4 with a choke, it could easily be a transformer. Look at Figure 1 below.

This image is copyright © by Ian C. Purdie VK2TIP - amplifier with shunt feedback and emitter degeneration
Figure 1 - amplifier with shunt feedback and emitter degeneration

Let's look at the choke RFC. What does it achieve for us?. Any inductor resists or opposes a change in current flowing in it. This has the effect of dumping any r.f. voltage through the C3 coupling capacitor.


What if we replace the RFC with a tuned circuit?. What benefits will accrue to us?.

  • we would introduce a measure of selectivity.

  • higher gain becomes possible

  • higher output power also becomes possible

  • Now let us review some our lessons from LC filters by examining a fairly basic LC resonant circuit as the load in place of our RFC.

    Now here in figure 2 is a bog standard LC resonant circuit which comprises an inductor and a capacitor. You will note there has been a link coupling wound on the inductor.

    Firstly the inductor could be of a fixed value such as one wound on a toroid or it could be a variable type similar to the ones found in receivers and used as IF transformers. Secondly the capacitor could be a fixed standard value one (e.g. 100 pF) or it could be a fixed standard value with an additional parallel capacitance in the form of a trimmer capacitor.

    Either way we would have one variable element (inductor or capacitor) which allows us to tune to the frequency we want. Figure 2 uses a fixed capacitor with a parallel trimmer.

    This image is copyright © by Ian C. Purdie VK2TIP - a tuned LC filter as an amplifier load
    Figure 2 - a tuned LC filter as an amplifier load

    Here we are only mainly concerned here with the principle of a tuned circuit as a load. In this example we have a final load of 50 ohms connected to the output link coupling of our tuned circuit. Assume, just for discussion purposes, that in this example we needed a power output of 100 milliwatt from the amplifier and that we have available a power supply of 12V. Further,


    2 * Po = [Vcc - Ve]2 / R

    or [2* 0.1] = [12 - 3.22]2 / R

    or [2* 0.1] = [ 8.78 ]2 / R

    and R = 77 / 0.2

    = 385 ohms

    Therefore the load presented to the output of our amplifier needs to be 385 ohms. The impedance ratio is 385 / 50 or 7.7:1 and the turns ratio on the transformer (inductor) is the square root of that number or 2.775:1.

    Again for discussion let us say we are designing this resonant circuit to work in the 40 metre amateur radio band. If you have done the LC filter tutorial you would certainly know that the LC at 7.2 Mhz is about 490.

    Now contrary to popular belief you will NOT get terribly impressive results from a single resonator circuit. That is really not the purpose of our resonator here. It's purpose is one of impedance transfer. We could just as easily used a low pass filter or even a high pass filter to achieve the same effect.

    Let us choose an arbitrary inductance by selecting a suitable toroid core for the frequency. An Amidon T50-2 is a very such core. It has an AL factor of 49.

    Assume for convenience that we wind 28 turns of #22 wire on this toroid. This many turns will occupy the entire winding area. What inductance results?


    [ L / N2] = [ AL  / 1002]


    [ L / 282] = [ 49  / 1002]

    L = 3.84 uH

    With such an inductor at 7.2 Mhz where we have said the LC is 490 we would need a total capacitance of about 128 pF to resonate with it. This would be provided by a fixed value of say 120 pf together with perhaps a 20 pF trimmer as depicted in figure 6. The inductor needed 28 turns primary and the turns ratio was 2.775:1 so our secondary turns to connect up to a 50 ohm load must be 10 turns. Before you go any further just review all that again.

    Next we will have to check if our class A amplifier is going to remain linear and also prove our resonator circuit is no where near as flash as you might first think. More important, this particular design has potential deep flaws in it.

    Above while calculating the load resistance for 100 milliwatt of power output I told you:

    2 * Po = [Vcc - Ve]2 / RL


    [2* 0.1] = [12 - 3.22]2 / RL


    [2* 0.1] = [ 8.78 ]2 / RL


    RL = 77 / 0.2

    = 385 ohms

    What I didn't tell you, but some advanced students might have worked out, the amplifier signal voltage could follow this excursion:-

    on negative peaks down to zero before going into saturation and on positive peaks to 12V + 8.78V = 20.78V.

    Obviously the only linear portion is plus and minus the potential swing of 8.78V or 17.56V Pk to Pk. To be able to do this our current must fluctuate from zero to twice our Idc value of 0.7 mA.

    By using ohms law our load resistance, RL

    R= E pk / Idc

    = 8.78 / .0007 A

    = 12543 ohms

    All right what has gone wrong? Let's re-work that equation to get the Idc we should have:

    Idc = Vpk / RL

    = 8.78 / 385

    = 0.0223 A


    22.3 mA

    Clearly I should have gone about this design another way. What I should do is make a list in the correct order of procedures or steps and calculate my components from those steps.

    And if you think basic high school maths was a waste of time well check this out. There are no short cuts in life.

    Now here's what you gets for your money in figure 3

    This image is copyright © by Ian C. Purdie VK2TIP - a tuned LC filter as our final amplifier load
    Figure 3 - a tuned LC filter as our final amplifier load

    Another aspect which must be looked at most carefully is heatsinking. Our little 2N2222A is copping a lot of current and would require a decent heatsink. Actually I would consider using a T05 type transistor such as a 2N3866.

    Negative feedback output circuit

    We do not have to use the above output LC circuit all the time because it's performance leaves much to be desired. Why?

    We have an inductor of 3.84 uH used at 7.2 Mhz. It's inductive reactance is (2 * pi * 7.2 * 3.84) = 174 ohms. It would have an unloaded Q of about 160 i.e. Rp = QU * XL = 160 * 174 = 27840 ohms. This figure is the unloaded impedance. But we are connecting up to a 50 ohm load and are going to extract power from our little amplifier.

    Now we have designed for a RL of 469 ohms which appears in parallel with the Rp of 27840. After calculation, [ Rp * RL ] / [ Rp + RL ], you should get a net load of 461 ohms. Our gain is now really 461 / Re or 461 / 56 = 8.2 BUT the loaded Q, QL is RL / XL or in this case QL = 461 / 174 = 2.65.

    Alert students who have done and remembered the LC Filter Tutorial will know that our loaded bandwidth is Bw = Fo / QL  or here it's 7200 Khz / 2.65 = 2716 Khz or 2.7 Mhz WIDE. In short it sux!.

    What to do?. Well you can always go back and re-arrange all your design formula so you eventually get a better result. You could for example, connect the collector to a tap on the primary of the inductor, say about 9 turns up from the bottom of the schematic and reduce the secondary turns down to 3 turns. What effect does this have?.

    The ultimate load is still 50 ohms. The unloaded Q and inductive reactance remain unaltered so Rp is still 27840. What would change is this. Firstly the primary:secondary turns ratio is now 28:3 which when squared transforms the primary impedance up to:

    [ 28 / 3 ]2 * 50 = 4355 ohms

    which again is in parallel with Rp of 27840 making a net RL of 3766 ohms.

    QL is RL / XL

    which is:

    3766 / 174 = 21.64

    a profound change is it not?. Therefore Bw = Fo / QL  or here it's 7200 Khz / 21.64 = 332 Khz which is a more respectable figure. Of course you always believed you were going to get a narrow and razor sharp filter didn't you?.

    Hey what sort of load does the transistor see?

    Well a 28 turn primary which we just established has an impedance of 3766 ohms and the collector is tapped 9 turns from the bottom so it's as before 28:9 or

    RL of 3766 ohms / [ 28 / 9 ]2 = 389 ohms

    and gain is now 389 / 56 = 6.94 or nearly a quite respectable 17 dB voltage gain (ignoring any losses in the LC filter). That's about as thrilling as it gets.

    Low Pass Filter Approach With Negative Feedback

    Yes folks the output circuit could well have been a low pass LC filter designed to transform a desired RL of say 400 ohms to 50 ohms. The circuit would have looked like this.

    This image is copyright © by Ian C. Purdie VK2TIP - a Class A amplifier using negative feedback with low pass filter output
    Figure 4 - a Class A amplifier using negative feedback with low pass filter output

    Rfc is not critical, it just resists rf getting into supply line, any thing with a reactance of about 20,000 ohms will do. Just ensure it can safely carry the necessary current. XC1, XC2 and XL are components calculated per low pass filter design. XL should be made variable (that's what the red line indicates).

    When the output is terminated into an appropriate load and then monitored on a scope, the output change is quite profound whilst varying XL to proper resonance.

    I've added two more resistors in, one in the collector to aid stability and one more in the supply line.

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